Permanent magnet synchronous motor

ABSTRACT

A 10-pole 9-slot permanent magnet synchronous motor comprises a stator core including an annular yoke and a plurality of teeth. Each of the plurality of teeth has a winding portion around which a coil is wound. The plurality of teeth include three teeth groups. Each of the three teeth groups includes a first tooth, a second tooth, and a third tooth of the teeth group sequentially arranged in a rotational direction of a rotor and around which coils of one phase are wound. The first tooth, second tooth, and third tooth of each of the three teeth groups are sequentially arranged in the rotational direction of the rotor. A width of the winding portion of the third tooth is narrower than a rotational direction width of the winding portion of the first tooth.

CROSS REFERENCE TO RELATED APPLICATION

This application is a U.S. national stage application of International Patent Application No. PCT/JP2015/067472 filed on Jun. 17, 2015, the disclosure of which is incorporated herein by reference.

TECHNICAL FIELD

The present invention relates to a permanent magnet synchronous motor that rotates a rotor using magnetic fields generated by permanent magnets provided on the rotor and magnetic fields generated by currents flowing through coils wound on a stator.

BACKGROUND

In a 10-pole 9-slot permanent magnet synchronous motor having coils wound in concentrated winding, three adjacent teeth around which coils of the same phase are wound adjacent to each other, form one teeth group, and three teeth groups are arranged on a yoke. In the conventional synchronous motor described in Patent Literature 1, from among three adjacent teeth around which coils of the same phase are wound, the width of a rotor facing portion of the middle tooth is set wider than respective rotor facing portions of the two teeth on opposite sides to achieve higher efficiency and higher output.

PATENT LITERATURE

-   Patent Literature 1: Japanese Patent Application Laid-open     Publication No. 2000-253602

In the 10-pole 9-slot permanent magnet synchronous motor, with respect to the rotational direction of a rotor, from among the three adjacent teeth around which coils of the same phase are wound, an iron loss occurring in the tooth located in front of the middle tooth along the rotor rotational direction is smaller than an iron loss occurring in the tooth located behind the middle tooth along the rotor rotational direction. That is, the iron losses occurring in the three adjacent teeth around which coils of the same phase are wound are not even. As such, in the 10-pole 9-slot permanent magnet synchronous motor, the respective iron losses occurring in the three adjacent teeth around which coils of the same phase are wound are different. However, the conventional technique described in Patent Literature 1 does not further improve motor efficiency focusing on the iron losses and shapes of the teeth.

The present invention has been made in view of the above, and an object thereof is to provide a permanent magnet synchronous motor that further improves the motor efficiency.

SUMMARY

To solve the above problem and achieve the object, a 10-pole 9-slot permanent magnet synchronous motor according to the present invention includes a stator core including an annular yoke and a plurality of teeth arranged inward of the yoke apart in a circumferential direction of the yoke; and a rotor placed inward of the stator core. Each of the plurality of teeth has a portion around which a coil is wound. The plurality of teeth include three teeth groups. Each of the three teeth groups includes a first tooth, a second tooth, and a third tooth of the teeth group sequentially arranged in a rotational direction of the rotor and around which coils of one phase are wound. A width of the portion of the third tooth is narrower than a width of the portion of the first tooth.

Advantageous Effects of Invention

The permanent magnet synchronous motor according to the present invention further improves the motor efficiency.

BRIEF DESCRIPTION OF DRAWINGS

FIG. 1 is a transverse cross-sectional view of a permanent magnet synchronous motor according to a first embodiment of the present invention.

FIG. 2 is a fragmentary enlarged view of major parts of the permanent magnet synchronous motor according to the first embodiment of the present invention.

FIG. 3 is a graph illustrating the waveforms of respective inductive voltages generated in a set of coils forming a U phase and the waveform of a combined inductive voltage of these inductive voltages.

FIG. 4 is a graph illustrating the result of obtaining iron losses respectively occurring in three adjacent teeth around which coils of the same phase are wound in the permanent magnet synchronous motor according to the first embodiment of the present invention through electromagnetic field analysis to compare.

FIG. 5 is a fragmentary enlarged view of major parts of a permanent magnet synchronous motor according to a second embodiment of the present invention.

FIG. 6 is a graph illustrating the result of obtaining iron losses respectively occurring in three adjacent teeth around which coils of the same phase are wound in the permanent magnet synchronous motor according to the second embodiment of the present invention through electromagnetic field analysis to compare.

FIG. 7 is a graph illustrating inductive voltage ratios when the rotational direction width of the end of the central tooth from among three adjacent teeth around which coils of the same phase are wound is changed.

DETAILED DESCRIPTION

Permanent magnet synchronous motors according to embodiments of the present invention will be described in detail below with reference to the drawings. Note that these embodiments are not intended to limit the present invention.

First Embodiment

FIG. 1 is a transverse cross-sectional view of a permanent magnet synchronous motor according to a first embodiment of the present invention. The permanent magnet synchronous motor 100 includes a stator core 10 including an annular yoke 1 a and nine teeth 1 b arranged inward of the yoke 1 a apart in a circumferential direction of the yoke 1 a, and a rotor 2 placed inward of the stator core 10. The rotor 2 includes an annular rotor core 2 a formed of magnetic steel sheets laid one over another to be fixed on a shaft 3 and 10 permanent magnets 2 b arranged on the outer edge of the rotor core 2 a. The 10 permanent magnets 2 b are arranged alternately in a rotational direction such that adjacent permanent magnets 2 b differ in polarity so as to form five pole pairs of N and S poles. The “rotational direction” refers to the direction in which the rotor 2 rotates. Each of the permanent magnets 2 b is a rare-earth magnet or ferrite magnet.

The stator 1 includes: the annular yoke 1 a; nine teeth 1 b arranged inward of the yoke 1 a and arranged apart in a rotational direction and extending toward the center of the yoke 1 a; and a coil (6U1, 6U2, 6U3, 6V1, 6V2, 6V3, 6W1, 6W2, 6W3) wound around each of the nine teeth 1 b. The yoke 1 a and the nine teeth 1 b forming the stator 1 are formed by stacking a plurality of core pieces punched out of magnetic steel sheet base material. Because the nine teeth 1 b are arranged at equal intervals in the rotational direction, two adjacent teeth 1 b form a mechanical angle of 40° with respect to the center axis A of the stator 1 as the center. As such, a plurality of sets of three adjacent teeth 1 b, around which coils of the same phase are wound, are arranged on the yoke 1 a.

Each of the nine teeth 1 b includes a winding portion 1 b 1 extending from the inner circumferential surface of the yoke 1 a toward the center of the stator 1 and around which a coil 6 is to be wound in concentrated winding and a brim-shaped or umbrella-shaped end 1 b 2 formed at the end of the tooth 1 b to protrude in both rotational directions from the winding portion 1 b 1. The width of the winding portion 1 b 1 along a direction orthogonal to a radial direction of the stator 1 is uniform. The end 1 b 2 has a shape symmetrical when going along the rotational direction. With the end 1 b 2 being in a brim or umbrella shape, the synchronous motor is structured such that the magnetic forces of the permanent magnets 2 b of the rotor 2 are effectively interlinked with the teeth 1 b, so that torque can be improved. In the first embodiment, the rotational direction width of the end 1 b 2 is the same for each of three adjacent teeth 1 b around which coils of the same phase are wound. Hereinafter, the rotational direction width of the end 1 b 2 is referred to as an end width. Further, hereinafter, from among a set of three adjacent teeth 1 b around which coils of the same phase are wound, the tooth 1 b placed in the front of the set of three teeth along the rotational direction of the rotor 2 is referred to as a first tooth; the tooth 1 b placed behind the first tooth along the rotational direction of the rotor 2 is referred to as a second tooth; and the tooth 1 b placed behind the second tooth along the rotational direction of the rotor 2 is referred to as a third tooth.

In the stator core 10, a part surrounded by two adjacent teeth 1 b forms a slot 5, so that nine slots 5 are provided. The permanent magnet synchronous motor 100 has eight poles and nine slots for the relationship between the number of magnetic poles and the number of slots, and coils forming three phases are wound in concentrated winding around the nine teeth 1 b. Of these coils, coils of the same phase from among a U phase, a V phase, and a W phase are wound around the winding portions 1 b 1 of three adjacent teeth 1 b respectively.

Specifically, three coils 6U1, 6U2, and 6U3 forming the U phase are wound around the winding portions 1 b 1 of three adjacent teeth 1 b respectively. The winding direction of the coil 6U2 is opposite to that of the coil 6U1, and the winding direction of the coil 6U3 is opposite to that of the coil 6U2.

Three coils 6V1, 6V2, and 6V3 forming the V phase are wound around the winding portions 1 b 1 of three adjacent teeth 1 b respectively. The winding direction of the coil 6V2 is opposite to that of the coil 6V1, and the winding direction of the coil 6V3 is opposite to that of the coil 6V2.

Three coils 6W1, 6W2, and 6W3 forming the W phase are wound around the winding portions 1 b 1 of three adjacent teeth 1 b respectively. The winding direction of the coil 6W2 is opposite to that of the coil 6W1, and the winding direction of the coil 6W3 is opposite to that of the coil 6W2.

FIG. 2 is a fragmentary enlarged view of major parts of the permanent magnet synchronous motor according to the first embodiment of the present invention. FIG. 2 illustrates the set of three coils 6U1, 6U2 and 6U3 that form the U phase. In FIG. 2, it is assumed that the rotor 2 rotates counterclockwise. Further, in FIG. 2, from among a set of three adjacent teeth around which the coils 6U1, 6U2, and 6U3 are wound, the tooth in front along the rotational direction of the rotor 2 is referred to as a first tooth; the tooth behind the first tooth 1 bU1 is referred to as a second tooth; and the tooth behind the second tooth 1 bU2 is referred to as a third tooth.

In the permanent magnet synchronous motor 100, when the rotor 2 rotates, a phase difference occurs between the inductive voltage generated in the coil 6U1 wound around the first tooth 1 bU1 and the inductive voltage generated in the coil 6U2 wound around the second tooth 1 bU2. In the stator 1 according to the first embodiment, focusing on this phase difference, the teeth are formed in such a way that the width W1 of the winding portion 1 b 1 of the first tooth 1 bU1 is wider than the width W2 of the winding portion 1 b 1 of the second tooth 1 bU2. Further, the width W2 of the winding portion 1 b 1 of the second tooth 1 bU2 is set wider than the width W3 of the winding portion 1 b 1 of the third tooth 1 bU3. The respective widths of the winding portions 1 b 1 of three adjacent teeth 1 b around which the coils 6V1, 6V2, and 6V3 illustrated in FIG. 1 are wound also have the same relationship, and the respective widths of the winding portions 1 b 1 of three adjacent teeth 1 b around which the coils 6W1, 6W2, and 6W3 are wound also have the same relationship. The width of each winding portion 1 b 1 is the rotational direction width of the winding portion 1 b 1.

The reason why the respective widths of the winding portions 1 b 1 of three adjacent teeth around which coils of the same phase are wound are different will be described below.

First, the phase difference between the combined inductive voltage for the same phase and the inductive voltage generated in each coil of one set of coils forming that same phase will be described. Where the teeth are arranged at equal intervals in the rotational direction, two adjacent teeth form a mechanical angle of 40° with respect to the center axis A of the stator 1 as the center. The mechanical angle of 40° is equal to 360° divided by nine, the number of slots. If coils are respectively wound around three adjacent teeth in the same direction, a phase difference of a 200° electrical angle occurs between inductive voltages generated in the individual coils when the rotor 2, of which the number of magnetic poles is 10, rotates. The electrical angle of 200° is equal to the mechanical angle of 40° multiplied by four, the number of pole pairs.

When the rotor 2 rotates, from among the plurality of magnetic poles, the phase of the inductive voltage generated in the coil 6U2 due to a permanent magnet 2 b indicated by a reference symbol B passing by the second tooth 1 bU2 is delayed by an electrical angle of 200° relative to the phase of the inductive voltage generated in the coil 6U1 due to the permanent magnet 2 b indicated by the reference symbol B passing by the first tooth 1 bU1.

In contrast, if the winding direction of one of the coils 6U1 and 6U2 is opposite to that of the other, the inductive voltage value is inverted in the positive/negative sign. Thus, the phase of the inductive voltage generated in the coil 6U1 due to the permanent magnet 2 b indicated by the reference symbol B passing by the first tooth 1 bU1 is delayed by an electrical angle of 20° relative to the phase of the inductive voltage generated in the coil 6U2 due to the permanent magnet 2 b indicated by the reference symbol B passing by the second tooth 1 bU2. That is, the phase difference between the inductive voltages is a 20° electrical angle. This 20° is equal to the value obtained by subtracting 180° from 200°.

Likewise, if the winding direction of one of the coils 6U2 and 6U3 is opposite to that of the other, the inductive voltage is inverted in the positive/negative sign. Thus, the phase of the inductive voltage generated in the coil 6U1 due to the permanent magnet 2 b indicated by the reference symbol B passing by the third tooth 1 bU3 is delayed by an electrical angle of 20° relative to the phase of the inductive voltage generated in the coil 6U2 due to the permanent magnet 2 b indicated by the reference symbol B passing by the second tooth 1 bU2.

As such, in the 10-pole 9-slot permanent magnet synchronous motor 100, because the phase differences between the respective inductive voltages generated in a set of coils 6 forming the same phase become a close value, these are dealt with as windings of the same phase.

FIG. 3 is a graph illustrating the waveforms of the respective inductive voltages generated in a set of coils forming the U phase and the waveform of a combined inductive voltage of these inductive voltages.

The value of the U-phase combined inductive voltage illustrated in FIG. 3 is equal to the combined value of the inductive voltage generated in the coil 6U1, the inductive voltage generated in the coil 6U2, and the inductive voltage generated in the coil 6U3 illustrated in, e.g., FIG. 2. It is assumed that the phase of the U-phase combined inductive voltage coincides with the phase of the phase current flowing through the coils 6U1, 6U2, and 6U3. The phase of the inductive voltage generated in the coil 6U1 is advanced by an electrical angle of 20° relative to the U-phase combined inductive voltage; the phase of the inductive voltage generated in the coil 6U2 is the same as that of the U-phase combined inductive voltage; and the phase of the inductive voltage generated in the coil 6U3 is delayed by an electrical angle of 20° relative to the U-phase combined inductive voltage.

In order to generate torque in the permanent magnet synchronous motor, a sinusoidal current synchronous with the inductive voltage generated for each phase needs to flow through the coils of the corresponding phase. The generated torque varies with the phase of the inductive voltage for one phase and the phase of the current flowing through the coils, and in the case of the permanent magnet synchronous motor having a surface-arranged rotor whose permanent magnets are arranged on the surface of the rotor, the largest torque can be generated with the same current when the phase of the inductive voltage coincides with the phase of the current flowing through the coils. At this time, the relationship between the phase of the inductive voltage generated in the coil of each tooth and the phase of the current flowing through is as follows. A current whose phase is delayed relative to the inductive voltage generated in the coil of the first tooth flows; and a current whose phase is advanced relative to the inductive voltage generated in the coil of the third tooth flows.

The iron loss occurring in the stator iron core tends toward increasing as the magnetic flux density in the stator iron core becomes higher. When currents are conducted through the coils of the stator to generate output torque in the permanent magnet synchronous motor, because the magnetic flux generated from the coils is added to the magnetic flux generated from the permanent magnets, the magnetic flux density in the stator iron core increases, resulting in an increase in the iron loss. At this time, if the current is delayed in phase relative to the inductive voltage, the magnetic flux generated from the coils acts to increase the magnetic flux density in the iron core, and if the current is advanced in phase relative to the inductive voltage, the magnetic flux generated from the coils acts to decrease the magnetic flux density in the iron core. Hence, if the current is delayed in phase relative to the inductive voltage, the iron loss tends toward increasing, and if the current is advanced in phase relative to the inductive voltage, the iron loss tends toward decreasing.

As such, in the stator iron core of the 10-pole 9-slot permanent magnet synchronous motor, the phase advancement and delay of the phase current occur simultaneously. Hence, when the rotor 2 rotates as illustrated in FIG. 2, the iron loss occurring in the first tooth 1 bU1 is larger than the iron loss occurring in the second tooth 1 bU2. The iron loss occurring in the third tooth 1 bU3 is smaller than the iron loss occurring in the second tooth 1 bU2. That is, the respective iron losses occurring in three adjacent teeth around which coils of the same phase are wound are not even.

The inventor of the present application, focused on the differences between the respective iron losses occurring in three adjacent teeth around which coils of the same phase are wound. The inventor thought of the permanent magnet synchronous motor 100 that can improve motor efficiency by setting the width of the winding portion 1 b 1 of the tooth placed in the back of a set of three adjacent teeth, around which coils of the same phase are wound, along the rotational direction of the rotor 2 to be narrower than the width of the winding portion 1 b 1 of the tooth placed in the front of the set of three adjacent teeth, thereby shortening the circumferential length of the coil wound around the winding portion 1 b 1 of the tooth in the back to relatively reduce the copper loss of the coil.

FIG. 4 is a graph illustrating the result of comparison of the iron losses respectively occurring in three adjacent teeth around which coils of the same phase are wound in the permanent magnet synchronous motor according to the first embodiment of the present invention, where the iron losses are obtained through electromagnetic field analysis. The horizontal axis represents the output torque of the permanent magnet synchronous motor 100 generated when a current whose phase coincides with the phase of the phase inductive voltage is conducted through the coils. The iron loss ratio represented by the vertical axis indicates the proportions of the iron losses respectively occurring in the winding portion 1 b 1 of the first tooth and the winding portion 1 b 1 of the third tooth to the iron loss occurring in the winding portion 1 b 1 of the second tooth from among the three adjacent teeth around which coils of the same phase are wound.

In FIG. 4, it is assumed that three adjacent teeth around which coils of the same phase are wound are in the same shape. That is, it is assumed that, for each of three adjacent teeth around which coils of the same phase are wound, the width of the winding portion 1 b 1 is the same and that the end width is the same.

The iron loss ratio indicated by (1) is the proportion of the iron loss occurring in the winding portion 1 b 1 of the first tooth to the iron loss occurring in the winding portion 1 b 1 of the second tooth. The iron loss ratio indicated by (2) is the proportion of the iron loss occurring in the winding portion 1 b 1 of the second tooth to the iron loss occurring in the second tooth, e.g., at the time of rotation without load. The iron loss ratio indicated by (3) is the proportion of the iron loss occurring in the winding portion 1 b 1 of the third tooth to the iron loss occurring in the winding portion 1 b 1 of the second tooth.

According to data illustrated in FIG. 4, at the time of rotation without load, that is, when no current is conducted through the coils, there is no difference in iron loss. However when a current is conducted through the coils, the iron loss ratios (1), (2) become greater than the iron loss ratio (3) as the output torque of the permanent magnet synchronous motor 100 increases.

The magnetic flux density in the iron core increases as the cross-section area of the flux path in the iron core decreases, and thus as the magnetic flux density in the iron core increases, the iron loss also increases. In general, the iron loss occurring in the iron core material is said to increase in proportion to the magnetic flux density to the power of 1.6 in the case of hysteresis loss. Hence, if each of the radial direction width of a yoke part 1 a 1, the width of the winding portion 1 b 1, and the radial direction width of the end 1 b 2 is decreased by the same size to make the flux path narrower, increase in iron loss can be suppressed to a minimum by selecting part that is the lowest in magnetic flux density to make its flux path narrower. Part of the iron core where the degree of increase in the magnetic flux density is the lowest is the winding portion 1 b 1 from among the yoke part 1 a 1, the winding portion 1 b 1, and the end 1 b 2.

In the permanent magnet synchronous motor of the present embodiment, focusing on the winding portion 1 b 1, where the degree of increase in the magnetic flux density is the lowest, the width of the winding portion 1 b 1 of the third tooth is set narrower than the width of the winding portion 1 b 1 of the second tooth, and the width of the winding portion 1 b 1 of the second tooth is set narrower than the width of the winding portion 1 b 1 of the first tooth. The reason why the winding portions 1 b 1 of the third tooth is made the narrowest is that the iron loss occurring in the third tooth located in the back along the rotational direction of the rotor 2 from among three adjacent teeth which coils of the same phase are wound around is smaller than the respective iron losses occurring in the second tooth and the first tooth along the rotational direction of the rotor 2 as described previously. Thus, in the permanent magnet synchronous motor of the first embodiment, the circumferential length of the coil wound around the winding portion 1 b 1 of the third tooth can be made shorter than that of the coil wound around the winding portion 1 b 1 of the second tooth and shorter than that of the coil wound around the winding portion 1 b 1 of the first tooth with suppressing increase in the iron loss.

In the first embodiment, the widths of the winding portions 1 b 1 of three adjacent teeth around which coils of the same phase are wound are set sequentially narrower in the rotational direction of the rotor 2. That is, as illustrated in FIG. 2, the width of the winding portion 1 b 1 of the second tooth 1 bU2 is narrower than the width of the winding portion 1 b 1 of the first tooth 1 bU1, and the width of the winding portion 1 b 1 of the third tooth 1 bU3 is narrower than the width of the winding portion 1 b 1 of the second tooth 1 bU2. As described above, the respective iron losses occurring in three adjacent teeth around which coils of the same phase are wound are sequentially smaller in the rotational direction of the rotor 2. Thus, as in the first embodiment, by setting the respective widths of the winding portions 1 b 1 of the three adjacent teeth around which coils of the same phase are wound to be different correspondingly to the magnitudes of their iron losses sequential in the rotational direction of the rotor 2, the circumferential length of the coil can be shortened with suppressing the influence of increase in the iron loss to a low level, so that motor efficiency can be improved. Further, the amount of coil usage is suppressed, so that production cost can be further reduced.

Although in the first embodiment the respective widths of the winding portions 1 b 1 of three adjacent teeth around which coils of the same phase are wound are sequentially smaller in the rotational direction of the rotor 2, not being limited to this, the width of the winding portion 1 b 1 of the second tooth from among the three adjacent teeth around which coils of the same phase are wound may be wider than the width of the winding portion 1 b 1 of the first tooth. Even with this configuration, as long as the respective widths of the ends 1 b 2 of the three teeth are the same, motor efficiency can be improved without impairing the characteristic of the 10-pole 9-slot permanent magnet synchronous motor that it can reduce cogging torque.

Second Embodiment

FIG. 5 is a fragmentary enlarged view of major parts of a permanent magnet synchronous motor according to a second embodiment of the present invention. In the second embodiment, the same reference numerals are used to denote the same parts as in the first embodiment with description thereof being omitted, and only different parts will be described. In the permanent magnet synchronous motor 100A according to the second embodiment, the end width of the second tooth is set narrower than the end widths of the first and third teeth from among three adjacent teeth around which coils of the same phase are wound. Note that the end width of the third tooth is narrower than the end width of the first tooth.

In the example of FIG. 5, the end width of the second tooth 1 bU2 is 45°. The end width of the second tooth 1 bU2 is defined as follows. That is, the end width of the second tooth 1 bU2 is defined as a width measured from the middle of a slot opening 1 c 1 between the right circumferential direction end 1 b 21 of the second tooth 1 bU2 and the left circumferential direction end 1 b 22 of the first tooth 1 bU1 to the middle of a slot opening 1 c 2 between the left circumferential direction end 1 b 22 of the second tooth 1 bU2 and the right circumferential direction end 1 b 21 of the third tooth 1 bU3.

Further, in the permanent magnet synchronous motor 100A, the width of the winding portion 1 b 1 of the third tooth is set narrower than the width of the winding portion 1 b 1 of the first tooth, and the width of the winding portion 1 b 1 of the second tooth is set narrower than the width of the winding portion 1 b 1 of the third tooth. In the example of FIG. 5, the respective widths of the winding portions 1 b 1 of three adjacent teeth around which coils of the same phase are wound are set narrower in the order of W1, W3, and W2, but the widths W2 and W3 may be the same in size.

FIG. 6 is a graph illustrating the result of comparison of the iron losses respectively occurring in three adjacent teeth around which coils of the same phase are wound in the permanent magnet synchronous motor according to the second embodiment of the present invention, where the iron losses are obtained through electromagnetic field analysis. The horizontal axis represents the output torque of the permanent magnet synchronous motor 100A generated when a current whose phase coincides with the phase of the phase inductive voltage is conducted through the coils. The iron loss ratio represented by the vertical axis indicates the proportions of the iron losses respectively occurring in the winding portion 1 b 1 of the first tooth and the winding portion 1 b 1 of the third tooth to the iron loss occurring in the winding portion 1 b 1 of the second tooth from among the three adjacent teeth around which coils of the same phase are wound.

In FIG. 6, it is assumed that the respective widths of the winding portions 1 b 1 of the three adjacent teeth around which coils of the same phase are wound are the same and that the end width of the second tooth is 36°. The iron loss ratios (1) to (3) correspond to the iron loss ratios (1) to (3) in FIG. 4.

In the first embodiment, the end widths of three adjacent teeth, around which coils of the same phase are wound, are the same. In contrast, in the second embodiment, the end width of the second tooth is set narrower than the end widths of the first and third teeth. Hence, in the second embodiment, the iron loss occurring in the winding portion 1 b 1 of the first tooth is the largest as compared with the case where the end widths of three adjacent teeth, around which coils of the same phase are wound, are the same, whereas the iron losses occurring in the winding portions of the second tooth and of the third tooth in the back are the same in value. Accordingly, in the second embodiment, by setting the width of the winding portion 1 b 1 of the second tooth to be narrower than the width of the winding portion 1 b 1 of the third tooth or setting the width of the winding portion 1 b 1 of the second tooth to be the same as the width of the winding portion 1 b 1 of the third tooth, a balance in iron loss can be achieved.

Where the end width of the second tooth is 36°, the end width of the second tooth is equal to 36° that is the rotational direction width of each of a plurality of magnetic poles formed in the rotor. Thus, where the end width of the second tooth is 36°, the amount of magnetic flux interlinked with the coil wound around the second tooth is the largest. As described above, the phase of the inductive voltage generated in the second tooth, from among the three adjacent teeth around which coils of the same phase are wound, coincides with the phase of the phase inductive voltage. Hence, when a current whose phase coincides with the phase of the phase inductive voltage is conducted through the coils, the second tooth outputs the largest torque from among the three adjacent teeth around which coils of the same phase are wound. Because increasing the amount of magnetic flux interlinked with the second tooth leads to an improvement in the output of the synchronous motor, the synchronous motor in which the end width of the second tooth is narrower than those of the first and third teeth is larger in output and better in efficiency.

FIG. 7 is a graph illustrating inductive voltage ratios when the rotational direction width of the end of the second tooth from among three adjacent teeth around which coils of the same phase are wound is changed. The horizontal axis represents the end width of the second tooth. The vertical axis represents the combined inductive voltage ratio with respect to the combined inductive voltage of the same phase when the end width of the second tooth is 32°. As illustrated in FIG. 7, it is seen that the combined inductive voltage of the same phase is largest when the end width of the second tooth is 36°.

Meanwhile, in the second embodiment, since the end width of the second tooth is 36°, the balance between the iron losses occurring in the winding portions 1 b 1 of three adjacent teeth around which coils of the same phase are wound is different than in the case where the end widths of the three teeth are the same. In the second embodiment, in order to achieve a balance between the iron losses occurring in the winding portions 1 b 1 of three adjacent teeth around which coils of the same phase are wound, as the end width of the second tooth is made narrower, the width of the winding portion 1 b 1 of the second tooth is also made narrower. As such, motor efficiency can be further improved by making the width of the winding portion 1 b 1 of the second tooth narrower.

In the permanent magnet synchronous motor 100A of the second embodiment, as in the permanent magnet synchronous motor 100 of the first embodiment, the width of the winding portion 1 b 1 of the third tooth from among three adjacent teeth around which coils of the same phase are wound, is made narrower than the width of the winding portion 1 b 1 of the first tooth, and thus copper loss is reduced correspondingly to the shortening of the circumferential length of the coil, so that motor efficiency can be improved, that production cost can be reduced, and that the permanent magnet synchronous motor 100A can be made lighter in weight.

Although in the first and second embodiments a surface permanent magnet (SPM) type of rotor 2 whose permanent magnets 2 b are arranged on the outer edge of the rotor core 2 a is used, an interior permanent magnet (IPM) type of rotor 2 whose permanent magnets 2 b are embedded in the rotor core 2 a may be used. In the case of an IPM-type rotor, permanent magnets are fixed in a rotor core by inserting, through pressing in, the permanent magnets into magnet inserting holes formed in the rotor core or by coating an adhesive. Further, not being limited to the one having magnetic steel sheets laid one over another, the rotor core 2 a may be an integral core obtained by processing steel material, a resin core obtained by solidifying a mixture of resin and iron powder, or a dust core obtained by pressure forming magnetic powder, the type of core to be used varying according to the purpose and application.

As described above, the permanent magnet synchronous motor according to the first and second embodiments includes a stator core including an annular yoke and a plurality of teeth, and a rotor placed inward of the stator core. Each of the plurality of teeth has a winding portion around which a coil is wound. The plurality of teeth include three teeth groups. Each of the three teeth groups includes adjacent first, second, and third teeth of the teeth group around which coils of the same phase are wound. The first, second, and third teeth of each of the three teeth groups are sequentially arranged in a rotational direction of the rotor. The width of the winding portion of the third tooth is narrower than the width of the winding portion of the first tooth. With this configuration, the circumferential length of the coil wound around the winding portion of the third tooth can be shortened with relatively suppressing increase in the iron loss in the winding portion of the third tooth, and thus copper loss is reduced correspondingly to the shortening of the circumferential length of the coil, so that motor efficiency can be improved. Further, the amount of coil usage is suppressed, so that production cost can be reduced. Yet further, the weight of the coil is reduced correspondingly to the shortening of the circumferential length of the coil, so that the permanent magnet synchronous motor can be made lighter in weight.

The configuration shown in the above embodiments is illustrative of the content of the present invention, and it is possible to combine it with other publicly known techniques, and also part of the configuration can be omitted or changed without departing from the spirit of the present invention. 

1-5. (canceled)
 6. A 10-pole 9-slot stator core including an annular yoke and a plurality of teeth arranged inward of the yoke apart in a circumferential direction of the yoke, wherein each of the plurality of teeth has a portion around which a coil is wound, wherein the plurality of teeth include 3N number of teeth groups, wherein each of the 3N number of teeth groups includes a first tooth, a second tooth, and a third tooth of the 3N number of teeth group sequentially arranged in a rotational direction of the rotor and around which coils of one phase are wound, and wherein a width of the portion of the second tooth is narrower than a width of the portion of the third tooth, and N is an integer of one or greater.
 7. The stator core according to claim 6, wherein a width of an end of the second tooth is narrower than a width of an end of the first tooth.
 8. The stator core according to claim 6, wherein the width of the portion of the second tooth is narrower than a width of the portion of the third tooth, and the width of the portion of the third tooth is narrower than the width of the portion of the first tooth.
 9. The stator core according to claim 8, wherein a width measured from a slot opening between the second tooth and the first tooth to a slot opening between the second tooth and the third tooth is set at an angle of 36°.
 10. A permanent magnet synchronous motor comprising the stator core according to claim 6 and a rotor placed inward of the stator core.
 11. An air-conditioning apparatus comprising the permanent magnet synchronous motor according to claim
 10. 